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semiconductor technical data high voltage greenline ? power factor controller d suffix plastic package case 751k (so16) 16 1 116 13 12 11 10 9 2 3 4 5 6 7 8 (top view) 5.0 v ref restart delay voltage fb current sense zero current agnd line leb pin connections order this document by mc33368/d comp mult frequency clamp v cc gate pgnd p suffix plastic package case 648 (dip16) 16 1 116 13 12 11 10 9 2 3 4 5 6 7 8 (top view) 5.0 v ref restart delay voltage fb current sense zero current agnd line leb comp mult frequency clamp v cc gate pgnd so16 dip16 15 14 n/c n/c 1 motorola analog ic device data
? the mc33368 is an active power factor controller that functions as a boost preconverter in offline power supply applications. mc33368 is optimized for low power, high density power supplies requiring a minimum board area, reduced component count and low power dissipation. the narrow body soic package provides a small footprint. integration of the high voltage startup saves approximately 0.7 w of power compared to resistor bootstrapped circuits. the mc33368 features a watchdog timer to initiate output switching, a one quadrant multiplier to force the line current to follow the instantaneous line voltage a zero current detector to ensure critical conduction operation, a transconductance error amplifier, a current sensing comparator, a 5.0 v reference, an undervoltage lockout (uvlo) circuit which monitors the v cc supply voltage and a cmos driver for driving mosfets. the mc33368 also includes a programmable output switching frequency clamp. protection features include an output overvoltage comparator to minimize overshoot, a restart delay timer and cyclebycycle current limiting. ? lossless offline startup ? output overvoltage comparator ? leading edge blanking (leb) for noise immunity ? watchdog timer to initiate switching ? restart delay timer greenline is a trademark of motorola, inc. ordering information device operating temperature range package MC33368D t j = 25 to +125 c so16 mc33368p t j = 25 to + 125 c dip16 this document contains information on a new product. specifications and information herein are subject to change without notice. ? motorola, inc. 1997 rev 2
mc33368 2 motorola analog ic device data representative block diagram this device contains 240 active transistors. restart delay output overvoltage multiplier/ error amplifier current sense watchdogtimer/ zero current detector fb restart delay comp mult leb current sense zc det frequency clamp internal bias generator uvlo s s r q pwm line v cc v ref agnd gate pgnd frequency clamp maximum ratings (t a = 25 c, unless otherwise noted.) rating symbol value unit power supply voltage (transient) v cc 20 v power supply voltage (operating) v cc 16 v line voltage v line 500 v current sense, multiplier, compensation, voltage feedback, restart delay and zero current input voltage v in1 1.0 to +10 v leb input, frequency clamp input v in2 1.0 to +20 v zero current detect input i in 5.0 ma restart diode current i in 5.0 ma power dissipation and thermal characteristics p suffix, plastic package case 648 maximum power dissipation @ t a = 70 c p d 1.25 mw thermal resistance, junctiontoair r q ja 100 c/w power dissipation and thermal characteristics d suffix, plastic package case 751k maximum power dissipation @ t a = 70 c p d 450 mw thermal resistance, junctiontoair r q ja 178 c/w operating junction temperature t j 150 c operating ambient temperature t a 25 to +125 c storage temperature range t stg 55 to +150 c note: esd data available upon request.
mc33368 3 motorola analog ic device data electrical characteristics (v cc = 14.5 v, for typical values t a = 25 c, for min/max values t j = 25 to +125 c) characteristic symbol min typ max unit error amplifier input bias current (v fb = 5.0 v) i ib 0 1.0 m a input offset voltage (v comp = 3.0 v) v io 2.0 50 mv transconductance (v comp = 3.0 v) g m 30 51 80 m mho output source (v fb = 4.6 v, v comp = 3.0 v) output sink (v fb = 5.4 v, v comp = 3.0 v) i o i o 9.0 9.0 17.5 17.5 30 30 m a overvoltage comparator voltage feedback input threshold v fb(ov) 1.07 v fb 1.084 v fb 1.1 v fb v propagation time to output t p 705 ns multiplier input bias current, v mult (v fb = 0 v) i ib 0.2 1.0 m a input threshold, v comp v th(m) 1.8 2.1 2.4 v dynamic input voltage range v multiplier input v mult 0 to 2.5 0 to 3.5 compensation v comp v th(m) to (v th(m) + 1.0) v th(m) to (v th(m) + 2.0) multiplier gain (v mult = 0.5 v, v comp = v th(m) + 1.0 v) k 0.25 0.51 0.75 1/v k v cs threshold v mult v comp v th(m) voltage reference voltage reference (i o = 0 ma, t j = 25 c) v ref 4.95 5.0 5.05 v line regulation (v cc = 10 v to 16 v) reg line 5.0 100 mv load regulation (i o = 0 5.0 ma) reg load 5.0 100 mv total output variation over line, load and temperature v ref 4.8 5.2 v maximum output current i o 5.0 10 ma reference undervoltage lockout threshold v th 4.5 v zero current detector input threshold voltage (v in increasing) v th 1.0 1.2 1.4 v hysteresis (v in decreasing) v h 100 200 300 mv delay to output t pd 127 ns current sense comparator input bias current (v cs = 0 to 2.0 v) i ib 0.2 1.0 m a input offset voltage (v mult = 0.2 v) v io 4.0 50 mv maximum current sense input threshold (v comp = 5.0 v, v mult = 5.0 v) v th(max) 1.3 1.5 1.8 v delay to output (v leb = 12 v, v comp = 5.0 v, v mult = 5.0 v) (v cs = 0 to 5.0 v step, c l = 1.0 nf) t phl(in/out) 50 270 425 ns frequency clamp frequency clamp input threshold v th(fc) 1.9 2.0 2.1 v frequency clamp capacitor reset current (v fc = 0.5 v) i reset 0.5 1.7 4.0 ma frequency clamp disable voltage v dfc 7.3 8.0 v
mc33368 4 motorola analog ic device data electrical characteristics (continued) (v cc = 14.5 v, for typical values t a = 25 c, for min/max values t j = 25 to +125 c) characteristic unit max typ min symbol drive output source resistance (current sense = 0 v, v gate = v cc 1.0 v) sink resistance (current sense = 3.0 v, v gate = 1.0 v) r oh r ol 4.0 4.0 8.6 7.2 20 20 w output voltage rise time (25% 75%) (c l = 1.0 nf) t r 55 200 ns output voltage fall time (75% 25%) (c l = 1.0 nf) t f 70 200 ns output voltage in undervoltage (v cc = 7.0 v, i sink = 1.0 ma) v o(uv) 0.01 0.25 v leading edge blanking input bias current i bias 0.1 0.5 m a threshold (as offset from v cc ) (v leb increasing) v leb 1.0 2.25 2.75 v hysteresis (v leb decreasing) v h 100 270 500 mv undervoltage lockout startup threshold (v cc increasing) v th(on) 11.5 13 14.5 v minimum operating voltage after turnon (v cc decreasing) v shutdown 7.0 8.5 10 v hysteresis v h 4.5 v timer watchdog timer t dly 180 385 800 m s restart timer threshold v th(restart) 1.5 2.3 3.0 v restart pin output current (v restart = 0 v, v ref = 5.0 v) i restart 3.1 5.2 7.1 ma total device line startup current (v cc = 0 v, v line = 50 v) i su 5.0 16 25 ma line operating current (v cc = v th(on) , v line = 50 v) i op 3.0 12.9 20 ma v cc dynamic operating current (50 khz, c l = 1.0 nf) v cc static operating current (i o = 0) i cc 5.3 3.0 8.5 ma line pin leakage (v line = 500 v) i line 30 80 m a
mc33368 5 motorola analog ic device data v fb(ov) , overvoltage input threshold (% v ) v cs , current sense pin 6 threshold (v) 6.0 v 55 110 0.12 0.08 10 100 55 16 0.2 1.6 q , excess phase (degrees) 5.0 m s/div t a , ambient temperature ( c) v m , multiplier pin 5 input voltage (v) g m , transconductance ( mho) m f, frequency (hz) v fb , voltage feedback threshold d t a , ambient temperature ( c) v cs , current sense pin 6 threshold (v) figure 1. current sense input threshold versus multiplier input v m , multiplier pin 5 input voltage (v) figure 2. current sense input threshold versus multiplier input, expanded view v cc = 14 v t a = 25 c figure 3. reference voltage versus temperature figure 4. overvoltage comparator input threshold versus temperature figure 5. error amplifier transconductance and phase versus frequency figure 6. error amplifier transient response v cc = 14 v v cc = 14 v t a = 25 c v cc = 14 v v o = 2.0 to 4.0 v r l = 10 k w t a = 25 c phase transconductance change (mv) 1.2 1.0 0.6 0.4 0.2 0 12 8.0 4.0 0 4.0 80 60 40 20 0 20 0.06 0.05 0.03 0.02 0.01 0 109 108 107 106 4.0 v 2.0 v 0 v 1.0 v 0.04 0.07 0.8 1.4 0.6 1.4 2.2 3.0 0.06 0 0.06 0.12 0.20 25 0 25 50 75 125 100 25 0 25 50 75 100 125 100 1.0 k 10 k 100 k 1.0 m 10 m 0 30 60 90 120 150 180 v cc = 14 v fb v pin 4 = 4.0 v = 3.0 v = 2.75 v = 2.5 v = 2.25 v = 2.0 v = 3.75 v = 3.5 v = 3.25 v v pin 4 = 4.0 v = 3.0 v = 2.75 v = 2.5 v = 2.25 v = 2.0 v
mc33368 6 motorola analog ic device data 400 2.0 6.0 55 500 0.01 1000 20 55 1.80 output voltage (v) 200 ms/div i cc , supply current (ma) v cc , supply voltage (v) t dly , watchdog time delay ( s) t a , ambient temperature ( c) r ja(t) , thermal resistance t, time (s) output voltage (v) 5.0 m s/div v chg , quickstart charge voltage (v) t a , ambient temperature ( c) figure 7. quickstart charge current versus temperature figure 8. watchdog timer delay versus temperature figure 9. drive output waveform figure 10. supply current versus supply voltage figure 11. transient thermal resistance figure 12. low load detection response waveform v cc = 14 v c l = 1000 pf t a = 25 c c o = 1000 pf pin 3, 6, 8= gnd pin 5 = 1.0 k to gnd t a = 25 c voltage current output current (a) output voltage load current i chg , quickstart charge current (ma) m q junctiontoair ( c/w) v cc = 14 v v cc = 14 v 1.76 1.72 1.68 1.64 15 10 5.0 0 100 10 200 0 4.0 2.0 0 460 420 380 340 25 0 25 50 75 100 125 25 0 25 50 75 100 125 4.0 6.0 8.0 10 12 14 0.1 1.0 10 100 3.0 2.0 1.0 0 1.50 1.30 1.10 0.90 0.70 5.0 pulse tested with a 4.0 v peak, 50 khz square wave through a 22 k resistance into pin 7.
mc33368 7 motorola analog ic device data functional description introduction with the goal of exceeding the requirements of legislation on line current harmonic content, there is an ever increasing demand for an economical method of obtaining a unity power factor. this data sheet describes a monolithic control ic that was specifically designed for power factor control with minimal external components. it offers the designer a simple cost effective solution to obtain the benefits of active power factor correction. most electronic ballasts and switching power supplies use a bridge rectifier and a bulk storage capacitor to derive raw dc voltage from the utility ac line, figure 13. figure 13. uncorrected power factor circuit rectifiers converter bulk storage capacitor load ac line this simple rectifying circuit draws power from the line when the instantaneous ac voltage exceeds the capacitor voltage. this occurs near the line voltage peak and results in a high charge current spike, figure 14. since power is only taken near the line voltage peaks, the resulting spikes of current are extremely nonsinusoidal with a high content of harmonics. this results in a poor power factor condition where the apparent input power is much higher than the real power. power factor ratios of 0.5 to 0.7 are common. figure 14. uncorrected power factor input waveforms rectified dc 0 v pk line sag ac line voltage ac line current 0 power factor correction can be achieved with the use of either a passive or active input circuit. passive circuits usually contain a combination of large capacitors, inductors, and rectifiers that operate at the ac line frequency. active circuits incorporate some form of a high frequency switching converter for the power processing with the boost converter being the most popular topology. since active input circuits operate at a frequency much higher than that of the ac line, they are smaller, lighter in weight, and more efficient than a passive circuit that yields similar results. with proper control of the preconverter, almost any complex load can be made to appear resistive to the ac line, thus significantly reducing the harmonic current content. operating description the mc33368 contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. referring to the block diagram in figure 15, note that a multiplier has been added to the current sense loop and that this device does not contain an oscillator. a description of each of the functional blocks is given below. error amplifier an error amplifier with access to the inverting input and output is provided. the amplifier is a transconductance type, meaning that it has high output impedance with controlled voltagetocurrent gain (g m 50 m mhos). the noninverting input is internally biased at 5.0 v 2.0%. the output voltage of the power factor converter is typically divided down and monitored by the inverting input. the maximum input bias current is 1.0 m a which can cause an output voltage error that is equal to the product of the input bias current and the value of the upper divider resistor r2. the error amplifier output is internally connected to the multiplier and is pinned out (pin 4) for external loop compensation. typically, the bandwidth is set below 20 hz so that the amplifier's output voltage is relatively constant over a given ac line cycle. in effect, the error amplifier monitors the average output voltage of the converter over several line cycles resulting in a fixed drive output ontime. the amplifier output stage can sink and source 11.5 m a of current and is capable of swinging from 1.7 to 5.0 v, assuring that the multiplier can be driven over its entire dynamic range. note that by using a transconductance type amplifier, the input is allowed to move independently with respect to the output, since the compensation capacitor is connected to ground. this allows dual usage of the voltage feedback pin by the error amplifier and overvoltage comparator. overvoltage comparator an overvoltage comparator is incorporated to eliminate the possibility of runaway output voltage. this condition can occur during initial startup, sudden load removal, or during output arcing and is the result of the low bandwidth that must be used in the error amplifier control loop. the overvoltage comparator monitors the peak output voltage of the converter, and when exceeded, immediately terminates mosfet switching. the comparator threshold is internally set to 1.08 v ref . in order to prevent false tripping during normal operation, the value of the output filter capacitor c3 must be large enough to keep the peaktopeak ripple less than 16% of the average dc output.
mc33368 8 motorola analog ic device data multiplier a single quadrant, two input multiplier is the critical element that enables this device to control power factor. the ac haversines are monitored at pin 5 with respect to ground while the error amplifier output at pin 4 is monitored with respect to the voltage feedback input threshold. a graph of the multiplier transfer curve is shown in figure 1. note that both inputs are extremely linear over a wide dynamic range, 0 to 3.2 v for pin 5 and 2.5 to 4.0 v for pin 4. the multiplier output controls the current sense comparator threshold as the ac voltage traverses sinusoidally from zero to peak line. this has the effect of forcing the mosfet ontime to track the input line voltage, thus making the preconverter load appear to be resistive. pin 6 threshold 0.55 v pin 4 v pin 3 v pin 5 zero current detector the mc33368 operates as a critical conduction current mode controller, whereby output switch conduction is initiated by the zero current detector and terminated when the peak inductor current reaches the threshold level established by the multiplier output. the zero current detector initiates the next ontime by setting the r s latch at the instant the inductor current reaches zero. this critical conduction mode of operation has two significant benefits. first, since the mosfet cannot turnon until the inductor current reaches zero, the output rectifier's reverse recovery time becomes less critical allowing the use of an inexpensive rectifier. second, since there are no deadtime gaps between cycles, the ac line current is continuous thus limiting the peak switch to twice the average input current the zero current detector indirectly senses the inductor current by monitoring when the auxiliary winding voltage falls below 1.2 v. to prevent false tripping, 200 mv of hysteresis is provided. the zero current detector input is internally protected by two clamps. the upper 10 v clamp prevents input overvoltage breakdown while the lower 0.7 v clamp prevents substrate injection. an external resistor must be used in series with the auxiliary winding to limit the current through the clamps to 5.0 ma or less. current sense comparator and rs latch the current sense comparator r s latch configuration used ensures that only a single pulse appears at the drive output during a given cycle. the inductor current is converted to a voltage by inserting a groundreferenced sense resistor r7 in series with the source of output switch. this voltage is monitored by the current sense input and compared to a level derived from the multiplier output. the peak inductor current under normal operating conditions is controlled by the threshold voltage of pin 6 where: i pk pin 6 threshold r7 abnormal operating conditions occur when the preconverter is running at extremely low line or if output voltage sensing is lost. under these conditions, the current sense comparator threshold will be internally clamped to 1.5 v. therefore, the maximum peak switch current is: i pk(max) 1.5 v r7 with the component values shown in figure 15, the current sense comparator threshold, at the peak of the haversine, varies from 110 mv at 90 vac to 100 mv at 268 vac. the current sense input to drive output propagation delay is typically 200 ns. timer a watchdog timer function was added to the ic to eliminate the need for an external oscillator when used in stand alone applications. the timer provides a means to automatically start or restart the preconverter if the drive output has been off for more than 385 m s after the inductor current reaches zero. undervoltage lockout and quickstart the mc33368 has a 5.0 v internal reference brought out to pin 1 and capable of sourcing 10 ma typically. it also contains an undervoltage lockout (uvlo) circuit which suppresses the gate output at pin 11 if the v cc supply voltage drops below 8.5 v typical. a quickstart circuit has been incorporated to optimize converter startup. during initial startup, compensation capacitor c1 will be discharged, holding the error amplifier output below the multiplier's threshold. this will prevent drive output switching and delay bootstraping of capacitor c4 by diode d6. if pin 4 does not reach the multiplier threshold before c4 discharges below the lower smps uvlo threshold, the converter will hiccup and experience a significant startup delay. the quickstart circuit is designed to precharge c1 to 1.7 v. this level is slightly below the pin 4 multiplier threshold, allowing immediate drive output switching. restart delay a restart delay pin is provided to allow hiccup mode fault protection in case of a short circuit condition and to prevent the smps from repeatedly trying to restart after the input line voltage has been removed. when power is first applied, there is no startup delay, but subsequent cycling of the v cc voltage will result in delay times that are programmed by an external resistor and capacitor. the restart delay, pin 2, is a high impedance, so that an external capacitor can provide delay times as long as several seconds. if the smps output is short circuited, the transformer winding, which provides the v cc voltage to the control ic and the mc33368, will be unable to sustain v cc to the control circuits. the restart delay capacitor at pin 2 of the mc33368 prevents the high voltage startup transistor within the ic from maintaining the voltage on c4. after v cc drops below the uvlo threshold in the smps, the smps switching transistors are held off for the time programmed by the values of the restart capacitor (c9) and resistor (r8). in this manner, the smps switching transistors are operated at very low duty cyles, preventing their destruction. if the short circuit fault is removed, the power supply system will turn on by itself in a normal startup mode after the restart delay has timed out.
mc33368 9 motorola analog ic device data output switching frequency clamp in normal operation, the mc33368 operates the boost inductor in the critical mode. that is, the inductor current ramps to a peak value, ramps down to zero, then immediately begins ramping positive again. the peak current is programmed by the multiplier output within the ic. as the input voltage haversine declines to near zero, the output switch ontime becomes constant, rather than going to zero because of the small integrated dc voltage at pin 5 caused by c2, r3 and r5. because of this, the average line current does not exactly follow the line voltage near the zero crossings. the output switching frequency clamp remedies this situation to improve power factor and minimize emi generated in this operating region. the values of r10 and c7, as shown in figure 15, program a minimum offtime in the frequency clamp which overrides the zero current detect signal, forcing a minimum offtime. this allows discontinuous conduction operation of the boost inductor in the zero crossing region, and the average line current more nearly follows the voltage. the output switching frequency clamp function can be disabled by connecting the fc input, pin 13, to the v cc supply pin 12. for best results, the minimum offtime, determined by the values of r10 and c7, should be chosen so that t s(min) = t (on) + t (off)fc . output drive is inhibited when the voltage at the frequency clamp input is less than 2.0 v. when the output drive is high, c7 is discharged through an internal 100 m a current source. when the output drive switches low, c7 is charged through r10. the drive output is inhibited until the voltage across c7 reaches 2.0 v, establishing a minimim offtime where: t (off)fc r10 c7 log e 1 2 v cc output the ic contains a cmos output driver that was specifically designed for direct drive of power mosfets. the gate output is capable of up to 1500 ma peak current with a typical rise and fall time of 50 ns with a 1.0 nf load. additional internal circuitry has been added to keep the gate output in a sinking mode whenever the undervoltage lockout is active. this characteristic eliminates the need for an external gate pulldown resistor. the totempole output has been optimized to minimize crossconduction current during high speed operation.
mc33368 10 motorola analog ic device data table 1. design equations calculation formula notes converter output power p o v o i o calculate the maximum required output power. peak indicator current i l(pk) 22 p o vac (ll) calculated at the minimum required ac line voltage for output regulation. let the efficiency h = 0.92 for low line operation. inductance l p t v o 2 vac (ll) vac (ll) 2 2 v o p o let the switching cycle t = 40 m s for universal input (85 to 265 vac) operation and 20 m s for fixed input (92 to 138 vac, or 184 to 276 vac) operation. switch ontime t (on) 2p o l p vac 2 in theory, the ontime t (on) is constant. in practice, t (on) tends to increase at the ac line zero crossings due to the charge on capacitor c5. let vac = vac (ll) for initial t (on) and t (off) calculations. switch offtime t (off) t (on) v o 2 vac sin 1 the offtime t (off) is greatest at the peak of the ac line voltage and approaches zero at the ac line zero crossings. theta ( q ) represents the angle of the ac line voltage. minimum switch offtime t (off) min l p i l(pk) v o the offtime is at a minimum at ac line crossings. this equation is used to calculate t (off) as theta approaches zero. delay time t d r10c7ln v cc 2 v cc the delay time is used to override the minimum offtime at the ac line zero crossings by programming the frequency clamp with c7 and r10. switching frequency f 1 t (on) t (off) the minimum switching frequency occurs at the peak of the ac line voltage. as the ac line voltage traverses from peak to zero, t (off) approaches zero producing an increase in switching frequency. peak switch current r7 v cs i l(pk) set the current sense threshold v cs to 1.0 v for universal input (85 to 265 vac) operation and to 0.5 v for fixed input (92 to 138 vac, or 184 to 276 vac) operation. note that v cs must be less than 1.4 v. multiplier input voltage v m vac 2 r5 r3 1 set the mulltiplier input voltage v m to 3.0 v at high line. empirically adjust v m for the lowest distortion over the ac line voltage range while guaranteeing startup at minimum line. converter output voltage v o v ref r2 r1 1 i ib r1 the i ib r1 error term can be minimized with a divider current in excess of 100 m a. converter output peaktopeak ripple voltage v o(pp) i l(pk) 1 2 f ac c3 2 esr 2 the calculated peaktopeak ripple must be less than 16% of the average dc output voltage to prevent false tripping of the overvoltage comparator. refer to the overvoltage comparator text. esr is the equivalent series resistance of c3. error amplifier bandwidth bw g m 2 c1 the bandwidth is typically set to 20 hz. when operating at high ac line, the value of c1 may need to be increased. note : the following converter characteristics must be chosen: v o = desired output voltage. vac (ll) = ac rms minimum required operating line voltage for output regulation. i o = desired output current. d v o = converter output peaktopeak ripple voltage. vac = ac rms operating line voltage.
mc33368 11 motorola analog ic device data multiplier 8 c1 0.68 figure 15. 80 w power factor controller v rms pin pf i fund thd2357v o(pp) v o i o p o n(%) 90 79.7 0.999 0.89 0.5 0.15 0.09 0.06 0.09 3.0 244.4 0.31 76.01 95.4 100 79.3 0.998 0.79 0.5 0.14 0.09 0.08 0.10 3.0 242.9 0.31 75.54 95.3 110 78.9 0.997 0.72 0.5 0.16 0.13 0.08 0.10 3.0 242.9 0.31 75.30 95.4 120 78.5 0.996 0.66 0.5 0.15 0.12 0.08 0.13 3.0 243.0 0.31 75.57 96.3 130 78.1 0.994 0.60 0.5 0.14 0.12 0.07 0.14 3.0 243.0 0.31 75.57 96.7 138 77.8 0.991 0.57 0.5 0.15 0.14 0.08 0.14 3.0 243.0 0.31 75.57 97.1 power factor controller test data frequency clamp r s q r s s timer r zero current detect v ref leading edge blanking low load detect comp fb 6 leb 13 pgnd gate zcd v cc line rd agnd mc33368 16 12 7 11 10 fc 9 3 1 4 quickstart 1.08 x v ref overvoltage comparator set dominant 15 v q 5.0 v reference v o d5 mur130 c3 220 mtp8n50e q1 d6 1n4934 c4 100 t r4 22 k emi filter 92 to 270 vrms r7 0.1 0.25 w c5 1.0 r5 1.3 m r3 20 k c2 0.01 r1 10 k r2 470 k r8 10 k c9 330 m f d1 d3 d2 d4 r11 10 15 v c6 0.1 13/8.0 uvlo 1.2/1.0 r13 51 d8 not used: d7, c8, r6, r9 1n4744 1n4006 320 m h r s latch v ref v ref v ref cs to v cc pin 12 2 5 mult 1.5 v ac line input current harmonic distortion (% i fund ) dc output r10 10 c7 10 pf t: coilcraft n2881a primary = 62 turns of #22 awg secondary = 5 turns of #22 awg core = coilcraft pt2510, ee25 gap = 0.072 total for a primary inductance (lp) of 320 m h heatsink = aavid engineering inc., 590302b03600, or 593002b03400
mc33368 12 motorola analog ic device data figure 16. 175 w universal input power factor controller not used: d7, c7, c8, r6, r9, r10 t: coilcraft n2880a l = 870 m hy primary: 78 turns of #16 awg secondary: 6 turns of #18 awg core: coilcraft pt4215, ee4215 gap: 0.104 total v rms pin pf i fund thd2357v o(pp) v o i o p o n(%) 90 190.4 0.995 2.11 5.8 0.16 0.32 0.24 0.80 3.6 398.0 0.44 175.9 92.4 120 192.1 0.997 1.60 3.2 0.08 0.17 0.07 0.30 3.6 398.9 0.44 177.1 92.2 138 192.7 0.997 1.40 0.9 0.08 0.24 0.03 0.15 3.6 402.3 0.45 179.0 92.9 180 194.3 0.995 1.08 0.9 0.04 0.18 0.04 0.08 3.6 409.1 0.45 182.9 94.1 240 189.3 0.983 0.80 0.7 0.08 0.21 0.08 0.06 3.6 407.0 0.45 181.1 95.7 268 186.3 0.972 0.71 0.6 0.11 0.32 0.10 0.10 3.6 406.2 0.44 180.4 96.8 ac line input current harmonic distortion (% i fund ) dc output multiplier 8 c1 2.2 frequency clamp r s q r s s timer r zero current detect v ref leading edge blanking low load detect comp fb 6 leb 13 pgnd gate zcd v cc line rd agnd mc33368 16 12 7 11 10 fc 9 3 1 4 quickstart 1.08 x v ref overvoltage comparator set dominant 1.5 v 15 v q 5.0 v reference v o d5 mur460 c3 330 mtw20n50e q1 d6 1n4934 c4 100 t r4 22 k emi filter 92 to 270 vrms r7 0.1 c5 1.0 r5 1.3 m r3 10 k c2 0.01 r1 10 k r2 820 k r8 1.0 m c9 2.2 d1 d3 d2 d4 r11 10 15 v c6 0.1 13/8.0 uvlo 1.2/1.0 r13 51 d8 1n4744 1n5406 r s latch v ref v ref v ref cs 2 5 mult power factor controller test data 6.9 v to v cc pin 12 heatsink = aavid engineering inc., 590302b03600
mc33368 13 motorola analog ic device data figure 17. power factor test setup 10 ac power analyzer pm 1000 a v voltech emi filter t 2x stepup isolation transformer autoformer 115 vrms input line neutral 0 to 270 vac output to power factor correction circuit hi hi l.o. l.o. 0.1 1.0 wvapfv rms a rms v d acf ainst freq harm an rfi filter is required for best performance when connecting the preconverter directly to the ac line. the filter attenuates the level of high frequency switching that appears on the ac line current waveform. figures 15 and 16 work well with commercially available two stage filters such as the delta electronics 03dpcg6. shown above is a single stage test filter that can easily be constructed with four ac line rated capacitors and a commonmode transformer. coilcraft cmt3282 was used to test figures 15 and 16. it has a minimum inductance of 28 mh and a maximum current rating of 2.0 a. coilcraft cmt4179 was used to test figure 19. it has a minimum inductance of 17 mh and a maximum current rating of 9.0 a. circuit conversion efficiency h (%) was calculated without the power loss of the rfi filter. figure 18. on/off control multiplier 8 c1 22 frequency clamp r s q r s s timer r v ref leading edge blanking low load detect comp fb 6 leb 13 pgnd gate zcd v cc line rd agnd mc33368 16 12 7 11 10 fc 9 3 1 4 quickstart overvoltage comparator set dominant 1.5 v 15 v q 5.0 v reference dc out d5 c3 330 mtw14n50e q1 d6 c4 100 t r4 22 k emi filter 92 to 270 vrms r7 0.1 c5 1.0 r5 1.3 m r3 10 k c2 0.01 r1 10 k r2 820 k r8 10 k c9 330 m f d1 d3 d2 d4 r11 10 15 v c6 0.1 13/8.0 uvlo 1.2/1.0 r13 51 d8 r s latch v ref v ref v ref cs 2 5 mult v cc 6.9 v 1.0 k 10 k 1.0 k 2n3904 1n4148 on/off input zero current detect 1.08 x v ref 5.0 v off 0 v on
mc33368 14 motorola analog ic device data figure 19. 400 w power factor controller multiplier 8 c1 1.0 frequency clamp r s q r s s timer r v ref leading edge blanking low load detect comp fb 6 leb 13 pgnd gate zcd v cc line rd agnd mc33368 16 12 7 11 10 fc 9 3 1 4 quickstart overvoltage comparator set dominant 1.5 v 15 v q 5.0 v reference 400 v mur460 d5 c3 330 mtw20n50e q1 d6 c4 100 t r4 22 k emi filter 92 to 270 vac r7 0.1 c5 1.0 r5 1.3 m r3 10.5 k c2 0.01 r1 10 k r2 820 k r8 1.0 m c9 330 m f d1 d3 d2 d4 r11 10 15 v c6 0.1 13/8.0 uvlo 1.2/1.0 r13 51 d8 r s latch v ref v ref v ref cs 2 5 mult 1.5 v zero current detect 1.08 x v ref 1n5406 r10 10 k c7 470 pf v ref c8 0.001 r9 10 1n4744 1n4934
mc33368 15 motorola analog ic device data ????? ????? ????? ????? ????? ????? ??? figure 20. printed circuit board and component layout (circuits of figures 15 and 16) dc output c6 r3 c2 d1 d3 ac input c5 transformer d5 dg s d8 j j j r10 c7 c9 r2 r8 c1 r4 c8 d6 r6 d2 d4 r5 r1 d7 ic1 r11 r9 j r13 r7 c4 q1 (top view) (bottom view) 4.5 3.0 mc33368 c3 j = jumper
mc33368 16 motorola analog ic device data p suffix plastic package case 64808 (dip16) issue r outline dimensions d suffix plastic package case 751k01 (so16) issue o 0.25 (0.010) s m s t notes: 1 dimensioning and tolerancing per ansi y14.5m, 1982. 2 controlling dimension: millimeter. 3 dimensions a and b do not include mold protrusion. 4 maximum mold protrusion 0.15 (0.006) per side. 5 dimension d does not include dambar protrusion. allowable dambar protrusion shall be 0.127 (0.005) total in excess of the d dimension at maximum material condition. dim a min max min max inches 9.80 10.00 0.368 0.393 millimeters b 3.80 4.00 0.150 0.157 c 1.35 1.75 0.054 0.068 d 0.35 0.49 0.014 0.019 f 0.40 1.25 0.016 0.049 g 1.27 bsc 0.050 bsc j 0.19 0.25 0.008 0.009 k 0.10 0.25 0.004 0.009 m 0 7 0 7 p 5.80 6.20 0.229 0.244 r 0.25 0.50 0.010 0.019 18 9 16 -a- g p ab 0.25 (0.010) s m b c k d 14 pl -t- seating plane j r x 45 m -b- f notes: 1. dimensioning and tolerancing per ansi y14.5m, 1982. 2. controlling dimension: inch. 3. dimension l to center of leads when formed parallel. 4. dimension b does not include mold flash. 5. rounded corners optional. a b f c s h g d j l m 16 pl seating 18 9 16 k plane t m a m 0.25 (0.010) t dim min max min max millimeters inches a 0.740 0.770 18.80 19.55 b 0.250 0.270 6.35 6.85 c 0.145 0.175 3.69 4.44 d 0.015 0.021 0.39 0.53 f 0.040 0.70 1.02 1.77 g 0.100 bsc 2.54 bsc h 0.050 bsc 1.27 bsc j 0.008 0.015 0.21 0.38 k 0.110 0.130 2.80 3.30 l 0.295 0.305 7.50 7.74 m 0 10 0 10 s 0.020 0.040 0.51 1.01 motorola reserves the right to make changes without further notice to any products herein. motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. atypicalo parameters which may be provided in motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. all operating parameters, including atypicalso must be validated for each customer application by customer's technical experts. motorola does not convey any license under its patent rights nor the rights of others. motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the motorola product could create a situation where personal injury or death may occur. should buyer purchase or use motorola products for any such unintended or unauthorized application, buyer shall indemnify and hold motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that motorola was negligent regarding the design or manufacture of the part. motorola and are registered trademarks of motorola, inc. motorola, inc. is an equal opportunity/affirmative action employer. mfax is a trademark of motorola, inc. how to reach us: usa / europe / locations not listed : motorola literature distribution; japan : nippon motorola ltd.; tatsumispdjldc, 6f seibubutsuryucenter, p.o. box 5405, denver, colorado 80217. 3036752140 or 18004412447 3142 tatsumi kotoku, tokyo 135, japan. 81335218315 mfax ? : rmfax0@email.sps.mot.com touchtone 6 022446609 asia / pacific : motorola semiconductors h.k. ltd.; 8b tai ping industrial park, internet : http://www.mot.com/sps/ 51 ting kok r oad, tai po, n.t., hong kong. 85226629298 mc33368/d ?

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